參數(shù)資料
型號： ISL8102CRZ-T
廠商： INTERSIL CORP
元件分類： 穩(wěn)壓器
英文描述： Two-Phase Buck PWM Controller with High Current Integrated MOSFET Drivers
中文描述： SWITCHING CONTROLLER, PQCC32
封裝： 5 X 5 MM, ROHS COMPLIANT, PLASTIC, MO-220VHHD-2, MLFP-32
文件頁數(shù)： 22/27頁
文件大小： 711K
代理商： ISL8102CRZ-T
22
FN9247.0
October 19, 2005
The compensation network consists of the error amplifier
(internal to the ISL8102) and the external R
1
-R
3
, C
1
-C
3
components. The goal of the compensation network is to
provide a closed loop transfer function with high 0dB crossing
frequency (F
0
; typically 0.1 to 0.3 of F
SW
) and adequate
phase margin (better than 45 degrees). Phase margin is the
difference between the closed loop phase at F
0dB
and 180°.
The equations that follow relate the compensation network’s
poles, zeros and gain to the components (R
1
, R
2
, R
3
, C
1
, C
2
,
and C
3
) in Figures 20 and 21. Use the following guidelines for
locating the poles and zeros of the compensation network:
1. Select a value for R
1
(1k
to 5k
, typically). Calculate
value for R
2
for desired converter bandwidth (F
0
). If
setting the output voltage to be equal to the reference set
voltage as shown in Figure 22, the design procedure can
be followed as presented. However, when setting the
output voltage via a resistor divider placed at the input of
the differential amplifier (as shown in Figure 6), in order
to compensate for the attenuation introduced by the
resistor divider, the obtained R
2
value needs be
multiplied by a factor of (R
P1
+R
S1
)/R
P1
. The remainder
of the calculations remain unchanged, as long as the
compensated R
2
value is used.
V
R
F
MAX
IN
LC
2. Calculate C
1
such that F
Z1
is placed at a fraction of the F
LC
,
at 0.1 to 0.75 of F
LC
(to adjust, change the 0.5 factor to
desired number). The higher the quality factor of the output
filter and/or the higher the ratio F
CE
/F
LC
, the lower the F
Z1
frequency (to maximize phase boost at F
LC
).
2
LC
3. Calculate C
2
such that F
P1
is placed at F
CE
.
C
2
1
CE
4. Calculate R
3
such that F
Z2
is placed at F
LC
. Calculate C
3
such that F
P2
is placed below F
SW
(typically, 0.5 to 1.0
times F
SW
). F
SW
represents the per-channel switching
frequency. Change the numerical factor to reflect desired
placement of this pole. Placement of F
P2
lower in frequency
helps reduce the gain of the compensation network at high
frequency, in turn reducing the HF ripple component at the
COMP pin and minimizing resultant duty cycle jitter.
R
LC
2
R
3
0.7 F
SW
It is recommended that a mathematical model is used to plot
the loop response. Check the loop gain against the error
amplifier’s open-loop gain. Verify phase margin results and
adjust as necessary. The following equations describe the
frequency response of the modulator (G
MOD
), feedback
compensation (G
FB
) and closed-loop response (G
CL
):
V
OSC
1
s f
( )
+
COMPENSATION BREAK FREQUENCY EQUATIONS
Figure 23 shows an asymptotic plot of the DC/DC converter’s
gain vs. frequency. The actual Modulator Gain has a high gain
peak dependent on the quality factor (Q) of the output filter,
which is not shown. Using the above guidelines should yield a
compensation gain similar to the curve plotted. The open loop
error amplifier gain bounds the compensation gain. Check the
compensation gain at F
P2
against the capabilities of the error
FIGURE 22. VOLTAGE-MODE BUCK CONVERTER
COMPENSATION DESIGN
-
+
E/A
VREF
COMP
C
1
R
2
R
1
FB
C
2
R
3
C
3
L
C
V
IN
PWM
CIRCUIT
HALF-BRIDGE
DRIVE
OSCILLATOR
ESR
EXTERNAL CIRCUIT
ISL8102
V
OUT
V
OSC
DCR
UGATE
PHASE
LGATE
-
+
VDIFF
VSEN
RGND
R
2
---------------------------------------------
=
C
1
----------------------------------------------
=
C
2
1
–
-------------------------------------------------------
=
R
3
------------
1
–
---------------------
=
C
3
------------------------------------------------
=
G
MOD
f
( )
-----------------------------
ESR
DCR
+
(
)
C
s
2
f
( )
L C
+
----------------------------------+
=
G
FB
f
( )
1
s f
( )
R
C
s f
( )
R
1
+
C
1
C
2
(
)
--------+
=
1
s f
( )
R
R
+
(
)
C
+
1
s f
( )
R
3
C
3
+
(
)
1
s f
( )
R
2
2
1
C
2
---------+
+
-------------------------------------------------------------------------------------------------------------------------
G
CL
f
( )
G
MOD
f
( )
G
FB
f
( )
=
where s f
( )
2
π
=
F
Z1
2
1
------------------------------
=
F
Z2
1
R
3
)
C
3
-----------------------+
=
F
P1
2
π
R
2
2
1
C
2
---------+
--------------------------------------------
=
F
P2
3
3
------------------------------
=
ISL8102
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