參數(shù)資料
型號(hào)： AD9631ARZ-REEL7
廠商： Analog Devices Inc
文件頁(yè)數(shù)： 7/20頁(yè)
文件大?。?/td> 0K
描述： IC OPAMP VF ULDIST 70MA 8SOIC
標(biāo)準(zhǔn)包裝： 750
放大器類(lèi)型： 電壓反饋
電路數(shù)： 1
轉(zhuǎn)換速率： 1300 V/µs
-3db帶寬： 320MHz
電流 - 輸入偏壓： 2µA
電壓 - 輸入偏移： 3000µV
電流 - 電源： 17mA
電流 - 輸出 / 通道： 70mA
電壓 - 電源，單路/雙路(±)： 6 V ~ 12 V，±3 V ~ 6 V
工作溫度： -40°C ~ 85°C
安裝類(lèi)型： 表面貼裝
封裝/外殼： 8-SOIC（0.154"，3.90mm 寬）
供應(yīng)商設(shè)備封裝： 8-SO
包裝： 帶卷 (TR)
Data Sheet
AD9631/AD9632
Rev. D | Page 15 of 20
THEORY OF OPERATION
GENERAL
The AD9631/AD9632 are wide bandwidth, voltage feedback
amplifiers. Because their open-loop frequency response follows
the conventional 6 dB/octave roll-off, their gain bandwidth
product is basically constant. Increasing their closed-loop gain
results in a corresponding decrease in small signal bandwidth.
This can be observed by noting the bandwidth specification
between the AD9631 (gain of +1) and AD9632 (gain of +2). The
AD9631/AD9632 typically maintain 65° of phase margin. This
high margin minimizes the effects of signal and noise peaking.
FEEDBACK RESISTOR CHOICE
The value of the feedback resistor is critical for optimum per-
formance on the AD9631 (gain of +1) and less critical as the
gain increases. Therefore, this section is specifically targeted
At the minimum stable gain (+1), the AD9631 provides opti-
mum dynamic performance with RF = 140 Ω. This resistor acts
as a parasitic suppressor only against damped RF oscillations
that can occur due to lead (input, feedback) inductance and
parasitic capacitance. This value of RF provides the best combi-
nation of wide bandwidth, low parasitic peaking, and fast
settling time.
In fact, for the same reasons, place a 100 Ω to 130 Ω resistor in
series with the positive input for other AD9631 noninverting
and all AD9631 inverting configurations. The correct connec-
tion is shown in Figure 59 and Figure 60.
Figure 59. Noninverting Operation
Figure 60. Inverting Operation
When the AD9631 is used in the transimpedance (I to V)
mode, such as in photodiode detection, the value of RF and
diode capacitance (CI) are usually known. Generally, the value
of RF selected will be in the k range, and a shunt capacitor (CF)
across RF will be required to maintain good amplifier stability.
The value of CF required to maintain optimal flatness (<1 dB
peaking) and settling time can be estimated by
(
)
[
]2
1
2
/
1
2
F
O
F
I
O
F
R
C
ω
where:
ωO is equal to the unity gain bandwidth product of the amplifier
in rad/sec.
CI is the equivalent total input capacitance at the inverting input.
Typically ωO = 800 × 106 rad/sec (see Figure 19).
As an example, choosing RF = 10 k and CI = 5 pF requires CF
to be 1.1 pF (Note that CI includes both source and parasitic
circuit capacitance). The bandwidth of the amplifier can be
estimated using CF:
F
3dB
C
R
f
π
2
6
.
1
Figure 61. Transimpedance Configuration
For general voltage gain applications, the amplifier bandwidth
can be closely estimated as
(
)
G
F
O
3dB
R
f
/
1
2
+
π
ω
This estimation loses accuracy for gains of +2/1 or lower due
to the damping factor of the amplifier. For these low gain cases,
the bandwidth will actually extend beyond the calculated value
As a general rule, Capacitor CF will not be required if
(
)
O
I
G
F
NG
C
R
ω
4
≤
×
where NG is the noise gain (1 + RF/RG) of the circuit. For most
voltage gain applications, this should be the case.
+VS
0.1F
10F
–VS
100Ω TO
130Ω
RIN
RTERM
VIN
VOUT
RF
RG
RF
RG
G = 1 +
AD9631/
AD9632
00601-
059
+VS
0.1F
10F
–VS
RTERM
VIN
VOUT
RF
RG
RF
RG
G = 1 –
AD9631/
AD9632
100Ω TO
130Ω
RIN
00601-
060
VOUT
RF
CF
CI
II
AD9631
00601-
061
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