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參數(shù)資料
| 型號： | SA1630 |
| 廠商： | NXP Semiconductors N.V. |
| 英文描述： | IF Quadrature Transceiver(IF正交收發(fā)器) |
| 中文描述： | 中頻正交收發(fā)器（中頻正交收發(fā)器） |
| 文件頁數(shù)： | 29/36頁 |
| 文件大?。?/td> | 477K |
| 代理商： | SA1630 |
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Philips Semiconductors
Application note
AN2003
SA1630 IF transceiver demonstration board
1999 Jan 05
29
The datasheet specifies a minimum of –30 dBc of carrier suppression with a differential input amplitude of 1 V
p-p
.
Substituting these values into Equation (109) gives:
X(0)
[1V
p
p
10
(
4
30 20)
]
7.9mV
(110)
Equation (110) tells us that for an ac input amplitude of 1V
p-p
, if the DC input offsets I(0) and Q(0) are assumed equal, and we assume ideal
quadrature phase and amplitude matching, the maximum DC offset allowed at the baseband inputs in order to meet the –30 dBc carrier
suppression specification is 7.9 mV. This value is most likely optimistic, but serves as an excellent reference when we look at the effects of
quadrature phase error and amplitude mismatch error on carrier suppression.
MORE PRACTICAL CONSIDERATIONS
Now that we have a better understanding of how offset, quadrature phase, and amplitude mismatch errors effect the carrier and sideband
suppression performance individually, let’s take a more practical look and consider the effects of simultaneous quadrature phase and amplitude
mismatch error on both carrier and sideband suppression.
Effect of simultaneous quadrature phase and amplitude errors on the carrier signal
Substituting the small angle approximations of Equations (19) and (20) into Equations (42) and (43) gives:
A =
1
/
2
G G
e
B =
1
/
2
G G
e
Θ
(111)
(112)
Substituting Equations (111) and (112) into the carrier signal expression Equation (39) gives:
C = G G
e
I(0) sin
ω
c
t + G G
e
Θ
I(0) cos
ω
c
t + G Q(0) cos
ω
c
t
(113)
Grouping terms gives:
C = G [(G
e
I(0)) sin
ω
c
t + (G
e
Θ
I(0) + Q(0)) cos
ω
c
t]
(114)
The magnitude of this signal will then be
mag(C)
G (G
e
I(0))
2
(G
e
I(0)
Q(0))
2
(115)
If we again assume that the offsets I(0) and Q(0) are equal and substituting Equation (106) into Equation (115) then
mag(C)
G (G
e
X(0))
2
(G
e
X(0)
X(0))
2
(116)
Expanding Equation (116) gives:
mag(C)
G G
e2
X(0)
2
(G
e
)
2
X(0)
2
2(G
e
) X(0)
2
X(0)
2
(117)
Pulling the common X(0)
2
term out of the square root yields:
mag(C)
GX(0) G
e2
G
e
)
2
2G
e
1
(118)
Equation (118) shows an expression relating the magnitude of the unwanted carrier signal as a function of input offset error, and the quadrature
phase and amplitude mismatch errors are completely contained within the square root term in the equation.
Note that if we assume zero quadrature phase error (
Θ
= 0) and perfectly matched amplitude and gain (G
e
= 1), Equation (118) reduces to:
mag(C)
GX(0) 1
2
(1
0)
2
2 * 1 * 0
1
GX(0) 2
(119)
which agrees with Equation (103) when the offsets I(0) and Q(0) are assumed equal.
The carrier suppression performance cannot yet be evaluated because this value is relative to the wanted sideband signal, which in our case is
the LSB signal. So, let’s now consider the effects of simultaneous phase error and amplitude error on the upper and lower sideband signals.
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