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參數(shù)資料
| 型號(hào)： | MAX15003 |
| 廠(chǎng)商： | Maxim Integrated Products, Inc. |
| 英文描述： | Triple-Output Buck Controller with Tracking/Sequencing |
| 中文描述： | 三輸出buck控制器，提供跟蹤/排序功能 |
| 文件頁(yè)數(shù)： | 22/32頁(yè) |
| 文件大?。?/td> | 945K |
| 代理商： | MAX15003 |
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M
Triple-Output Buck Controller with
Tracking/Sequencing
22
______________________________________________________________________________________
The Type II compensator’s mid-frequency gain
(approximately 18dB shown here) is designed to com-
pensate for the power modulator’s attenuation at the
desired crossover frequency, f
CO
(G
E/A
+ G
MOD
= 0dB
at f
CO
). In this example, the power modulator’s inherent
-20dB/decade roll-off above the ESR zero (f
ZERO, ESR
)
is leveraged to extend the active regulation gain-band-
width of the voltage regulator. As shown in Figure 5b,
the net result is a 6x increase in the regulator’s gain
bandwidth while providing greater than 75° of phase
margin (the difference between G
E/A
and G
MOD
respective phases at crossover, f
CO
).
Other filter schemes pose their own problems. For
instance, when choosing high-quality filter capacitor(s),
e.g., MLCCs, and an inductor with minimal parasitics,
the inherent ESR zero may occur at a much higher fre-
quency, as shown in Figure 5c.
As with the previous example, the actual gain and
phase response is overlaid on the power modulator’s
asymptotic gain response. One readily observes the
more dramatic gain and phase transition at or near the
power modulator’s resonant frequency, f
LC
, versus the
gentler response of the previous example. This is due
to the component’s lower parasitics leading to the high-
er frequency of the inherent ESR zero of the output
capacitor. In this example, the desired crossover fre-
quency occurs below the ESR zero frequency.
In this example, a compensator with an inherent mid-
frequency double-zero response is required to mitigate
the effects of the filter’s double-pole. Such is available
with the Type III topology.
As demonstrated in Figure 5d, the Type III’s mid-
frequency double-zero gain (exhibiting a +20dB/
decade slope, noting the compensator’s pole at the ori-
gin) is designed to compensate for the power modula-
tor’s double-pole -40dB/decade attenuation at the
desired crossover frequency, f
CO
(again, G
E/A
+ G
MOD
= 0dB at f
CO
). (See Figure 5d).
In the above example, the power modulator’s inherent
(mid-frequency) -40dB/decade roll-off is mitigated by
the mid-frequency double zero’s +20dB/decade gain to
extend the active regulation gain-bandwidth of the volt-
age regulator. As shown in Figure 5d, the net result is
an approximate doubling in the regulator’s gain band-
width while providing greater than 60° of phase margin
(the difference between G
E/A
and G
MOD
respective
phases at crossover, f
CO
).
Design procedures for both Type II and Type III com-
pensators are shown below.
M
P
FREQUENCY (Hz)
-60
-40
-20
0
20
40
-80
-135
-90
-45
0
45
90
-180
POWER MODULATOR (HIGH-QUALITY OUTPUT
CAPACITORS (S)) GAIN (REAL, ASYMPTOTIC)/
PHASE RESPONSE vs. FREQUENCY
MAX15003 fig05c
100
1k
10k
100k
1M
10M
10
|G
MOD
|
|G
MOD
|
|G
MOD
|
f
LC
f
ZEROES
f
ZEROES
Figure 5c. Power Modulator Gain and Phase Response (High-
Quality COUT)
POWER MODULATOR (HIGH-QUALITY OUTPUT CAPACITOR(S))
AND TYPE III COMPENSATOR GAIN (ASYMPTOTIC)/
PHASE RESPONSE vs. FREQUENCY
80
M
P
FREQUENCY (Hz)
-60
-40
-20
0
20
40
60
-80
-203
-135
-68
0
68
135
203
270
-270
100
1k
10k
100k
1M
10M
10
< G
EA
|G
EA
|
|G
MOD
|
f
LC
f
ZEROES
f
ZEROES
f
CO
< G
MOD
Figure 5d. Power Modulator (High-Quality COUT) and Type III
Compensator Responses
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