參數(shù)資料
型號(hào)： ADA4817-1ARDZ-RL
廠商： Analog Devices Inc
文件頁(yè)數(shù)： 8/28頁(yè)
文件大小： 0K
描述： IC OPAMP VF 410MHZ LN 40MA 8SOIC
標(biāo)準(zhǔn)包裝： 2,500
系列： FastFET™
放大器類型： 電壓反饋
電路數(shù)： 1
轉(zhuǎn)換速率： 870 V/µs
增益帶寬積： 410MHz
-3db帶寬： 1.05GHz
電流 - 輸入偏壓： 2pA
電壓 - 輸入偏移： 400µV
電流 - 電源： 19mA
電流 - 輸出 / 通道： 40mA
電壓 - 電源，單路/雙路(±)： 5 V ~ 10 V，±2.5 V ~ 5 V
工作溫度： -40°C ~ 105°C
安裝類型： 表面貼裝
封裝/外殼： 8-SOIC（0.154"，3.90mm Width）裸露焊盤
供應(yīng)商設(shè)備封裝： 8-SOIC-EP
包裝： 帶卷 (TR)
ADA4817-1/ADA4817-2
Data Sheet
Rev. B | Page 16 of 28
Table 8. Power-Down Voltage Control
PD Pin
±5 V
+3 V, 2 V
Not active
>4 V
>2 V
Active
<2 V
<0 V
CAPACITIVE FEEDBACK
Due to package variations and pin-to-pin parasitics between the
single and the dual models, the ADA4817-2 has a little more
peaking then the ADA4817-1, especially at a gain of 2. The best
way to tame the peaking is to place a feedback capacitor across
the feedback resistor. Figure 46 shows the small signal frequency
response of the ADA4817-2 at a gain of 2 vs. CF. At first, no CF
was used to show the peaking, but then two other values of
0.5 pF and 1 pF were used to show how to reduce the peaking or
even eliminate it. As shown in Figure 46, if the power consumption
is a factor in the system, then using a larger feedback capacitor
is acceptable as long as a feedback capacitor is used across it to
control the peaking. However, if power consumption is not an
issue, then a lower value feedback resistor, such as 200 , would
not require any additional feedback capacitance to maintain
flatness and lower peaking.
9
6
3
0
–3
–6
–9
1M
10M
100M
1G
10G
C
LOS
E
D
-LOOP
GA
IN
(
dB
)
FREQUENCY (Hz)
07756-
049
RF = 348Ω
G = 2
VS = 10V
VOUT = 100mV p-p
RL = 100Ω
CF = 1pF
CF = 0.5pF
NO CF
Figure 46. Small Signal Frequency Response vs. Feedback Capacitor
(ADA4817-2)
HIGHER FREQUENCY ATTENUATION
There is another package variation problem between the SOIC
and the LFCSP package. The SOIC package shows approximately
1 dB to 1.5 dB of additional peaking at a gain of 1. This is due to
the parasitic in the SOIC package, which is not recommended
for very high frequency parts that exceed 1 GHz. A good approach
to reducing the peaking is to place a resistor, RS, in series with
the noninverting input. This creates a first-order pole formed
by RS and CIN, the common-mode input capacitance.
Figure 47 shows the higher frequency attenuation, which
reduces the peaking but also reduces the 3 dB bandwidth.
–9
–6
–3
0
3
6
1M
10M
100M
1G
10G
C
LOS
E
D
-LOOP
GA
IN
(
dB
)
FREQUENCY (Hz)
RS = 100
RS = 75
RS = 50
RS = 0
07756-
247
RL = 100Ω
VS = ±5V
VOUT = 0.1V p-p
G = 1
Figure 47. Small Signal Frequency Response for Various RS (SOIC)
As shown in Figure 47, the peaking dropped by almost 2 dB
when RS = 0 to RS = 100 , and in return, the 3 dB bandwidth
dropped from 1 GHz to 700 MHz. To maintain the 3 dB
bandwidth and to reduce peaking, an RLC circuit is recommended
instead of RS, as shown in Figure 48.
L
10nH
R
120
C
2pF
07756-
248
Figure 48. RLC Circuit
The R in parallel to the series LC forms a notch that can be
shaped to compensate for the peaking produced by the amplifier.
The result is a smooth 1 GHz 3 dB bandwidth, 250 MHz 0.1 dB
flatness, and less than 1 dB of peaking. This circuit should be
placed in the path of the noninverting input when the ADA4817-x
is used at a gain of 1. The RLC values may need tweaking
depending on the source impedance and the flatness and band-
width required. Figure 49 shows the frequency response after the
RLC circuit is in place.
–9
–6
–3
0
3
6
1M
10M
100M
1G
10G
C
LOS
E
D
-LOOP
GA
IN
(
dB
)
FREQUENCY (Hz)
RLC
NO RLC
07756-
249
RL = 100Ω
VS = 10V
VOUT = 100mV p-p
G = 1
Figure 49. Frequency Response with RLC Circuit
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